Drive methods for a three-phase motor

ABSTRACT

A method of driving a three-phase motor includes, while a first phase is energized, driving a second phase using a first drive function which is sinusoidal. The first phase is switched to a non-energized state and a back electromotive force (BEMF) voltage of the first phase is detected. For at least a portion of a time when the first phase is non-energized the driving of the second phase depends on the output of a second drive function different from the first drive function. The second drive function may be non-sinusoidal and may be a cosine function. The second drive function may drive the second phase when the output of the second drive function is a modulation ratio less than 1. When the output of the second drive function is a modulation ratio greater than or equal to 1 the second phase may be driven to a modulation ratio of 1.

BACKGROUND 1. Technical Field

Aspects of this document relate generally to methods of controllingthree-phase motors. Specific aspects of this document relate to methodsof controlling star-connected three-phase sensor-less motors.

2. Background

Three-phase motors use electricity applied to the motor in threedifferent phases to rotate the motor. The phases ordinarily involveseparate electrical connections and are commonly referred to as the Uphase, V phase, and W phase.

SUMMARY

Implementations of methods of driving a star-connected three-phase motormay include: while a first phase of the star-connected three-phase motoris in an energized state, driving a second phase of the three-phasemotor using a first sinusoidal drive function; and switching the firstphase to a non-energized state. The method may also include while thefirst phase is in the non-energized state, detecting a first backelectromotive force (BEMF) voltage of the first phase; and for at leasta portion of a time when the first phase is in the non-energized state,driving the second phase using a second drive function that varies fromthe first sinusoidal drive function.

Implementations of methods of driving a star-connected three-phase motormay include one, all, or any of the following:

The three-phase motor may be a sensorless brushless direct current(BLDC) motor or a permanent magnet synchronous motor (PMSM).

The method may include where driving the second phase using the seconddrive function may result in an increased voltage applied to the secondphase relative to driving the second phase using the first sinusoidaldrive function.

The method may include where while the first phase is in a secondnon-energized state, a third phase of the three-phase motor may bedriven using a third drive function that varies from a second sinusoidaldrive function.

The method may include where driving the third phase using the thirddrive function may result in an increased voltage applied to the thirdphase relative to driving the third phase using the second sinusoidaldrive function.

The method may include where after driving the second phase using thesecond drive function until the first BEMF voltage is detected, thesecond phase may be driven using the first sinusoidal drive function.

The method may include where after driving the second phase using thesecond drive function for a predetermined amount of time, the secondphase may be driven using the first sinusoidal drive function.

In implementations of the method, a graph plotting a generated torque ofthe three-phase motor on a y-axis and a rotor angle position of a rotorof the three-phase motor on an x-axis may display no variation in thegenerated torque over at least one powered 360-degree rotation of therotor.

Implementations of methods of driving a star-connected three-phase motormay include: driving a first phase of the star-connected three-phasemotor using a first sinusoidal drive function when all three phases areenergized; driving the first phase using a first non-sinusoidal drivefunction for at least a portion of a time when one phase other than thefirst phase is not energized and when the first non-sinusoidal drivefunction results in a modulation ratio less than 1. The method mayinclude driving the first phase to a modulation ratio of 1 for at leasta portion of a time when one phase other than the first phase is notenergized and when the first non-sinusoidal drive function results in amodulation ratio greater than or equal to 1.

Implementations of methods of driving a star-connected three-phase motormay include one, all, or any of the following:

The modulation ratios may be low torque ripple modulation ratios.

The first non-sinusoidal drive function may be a first cosine drivefunction.

The first cosine drive function may be

${\frac{M}{\cos( {\theta - \theta_{wc}} )}},$wherein M is a modulation ratio ranging from 0 to 1, wherein θ is anangle of rotation of the three-phase motor, and wherein θ_(wc) has avalue of 0 degrees when θ is less than 30 degrees and greater than orequal to 0 degrees, a value of 60 degrees when θ is less than 90 degreesand greater than or equal to 30 degrees, a value of 120 degrees when θis less than 150 degrees and greater than or equal to 90 degrees, avalue of 180 degrees when θ is less than 210 degrees and greater than orequal to 150 degrees, a value of 240 degrees when θ is less than 270degrees and greater than or equal to 210 degrees, a value of 300 degreeswhen θ is less than 330 degrees and greater than or equal to 270degrees, and a value of 0 degrees when θ is less than 360 degrees andgreater than or equal to 330 degrees.

The first sinusoidal drive function may be

${U_{2{pm}} = {\frac{2}{\sqrt{3}}M*\{ {U_{3{pm}} - {\min( {U_{3{pm}},V_{3{pm}},W_{3{pm}}} )}} \}}},{wherein}$${U_{3{pm}} = {\frac{1}{2}\sin\;\theta}},{V_{3{pm}} = {\frac{1}{2}{\sin( {\theta - {\frac{2}{3}\pi}} )}}},{W_{3{pm}} = {\frac{1}{2}{\sin( {\theta - {\frac{4}{3}\pi}} )}}},$wherein M is a modulation ratio ranging from 0 to 1, and wherein θ is anangle of rotation of the three-phase motor.

Implementations of the method may include where a second phase of thethree-phase motor may be driven using a second sinusoidal drive functionwhen all three phases are energized; the second phase may be drivenusing the first non-sinusoidal drive function for at least a portion ofa time when one phase other than the second phase is not energized andwhen the first non-sinusoidal drive function results in a modulationratio less than 1; and the second phase may be driven to a modulationratio of 1 for at least a portion of a time when one phase other thanthe second phase is not energized and when the first non-sinusoidaldrive function results in a modulation ratio greater than or equal to 1.

The second sinusoidal drive function may be

${V_{2{pm}} = {\frac{2}{\sqrt{3}}M*\{ {V_{3{pm}} - {\min( {U_{3{pm}},V_{3{pm}},W_{3{pm}}} )}} \}}},{wherein}$${U_{3{pm}} = {\frac{1}{2}\sin\;\theta}},{V_{3{pm}} = {\frac{1}{2}{\sin( {\theta - {\frac{2}{3}\pi}} )}}},{W_{3{pm}} = {\frac{1}{2}{\sin( {\theta - {\frac{4}{3}\pi}} )}}},$wherein M is a modulation ratio ranging from 0 to 1, and wherein θ is anangle of rotation of the three-phase motor.

Implementations of the method may include where a third phase of thethree-phase motor may be driven using a third sinusoidal drive functionwhen all three phases are energized; the third phase may be driven usingthe first non-sinusoidal drive function for at least a portion of a timewhen one phase other than the third phase is not energized and when thefirst non-sinusoidal drive function results in a modulation ratio lessthan 1; and the third phase may be driven to a modulation ratio of 1 forat least a portion of a time when one phase other than the third phaseis not energized and when the first non-sinusoidal drive functionresults in a modulation ratio greater than or equal to 1.

The third sinusoidal drive function may be

${W_{2pm} = {\frac{2}{\sqrt{3}}M*\{ {W_{3pm} - {\min( {U_{3pm},V_{3pm},W_{3pm}} )}} \}}},{{{wherein}\mspace{14mu} U_{3pm}} = {\frac{1}{2}\sin\;\theta}},\;{V_{3pm} = {\frac{1}{2}si{n( {\theta - {\frac{2}{3}\pi}} )}}},{W_{3pm} = {\frac{1}{2}\;{\sin( {\theta - {\frac{4}{3}\pi}} )}}},$wherein M is a modulation ratio ranging from 0 to 1, and wherein θ is anangle of rotation of the three-phase motor.

Implementations of methods of driving a three-phase motor may include:driving a U phase of the three-phase motor using a first sinusoidaldrive function when all three phases are energized; driving a V phase ofthe three-phase motor using a second sinusoidal drive function when allthree phases are energized; driving a W phase of the three-phase motorusing a third sinusoidal drive function when all three phases areenergized; and driving each phase using a cosine drive function for atleast a portion of a time when one other phase is not energized.

Implementations of methods of driving a three-phase motor may includeone, all, or any of the following:

The modulation ratios may be low torque ripple modulation ratios.

In various implementations of the method, each phase may be driven usingthe cosine drive function for at least a portion of a time when oneother phase is not energized and when the cosine drive function resultsin a modulation ratio less than 1, and each phase may be driven to amodulation ratio of 1 for at least a portion of a time when one otherphase is not energized and when the cosine drive function results in amodulation ratio greater than or equal to 1.

The cosine drive function may be

$\frac{M}{\cos( {\theta - \theta_{wc}} )}$wherein M is a modulation ratio ranging from 0 to 1, wherein θ is anangle of rotation of the three-phase motor, and wherein has a value of 0degrees when θ is less than 30 degrees and greater than or equal to 0degrees, a value of 60 degrees when θ is less than 90 degrees andgreater than or equal to 30 degrees, a value of 120 degrees when θ isless than 150 degrees and greater than or equal to 90 degrees, a valueof 180 degrees when θ is less than 210 degrees and greater than or equalto 150 degrees, a value of 240 degrees when θ is less than 270 degreesand greater than or equal to 210 degrees, a value of 300 degrees when θis less than 330 degrees and greater than or equal to 270 degrees, and avalue of 0 degrees when θ is less than 360 degrees and greater than orequal to 330 degrees.

The first sinusoidal drive function may be

${U_{2pm} = {\frac{2}{\sqrt{3}}M*\{ {U_{3pm} - {\min( {U_{3pm},V_{3{pm}},W_{3pm}} )}} \}}},$the second sinusoidal drive function may be

${V_{2pm} = {\frac{2}{\sqrt{3}}M*\{ {V_{3pm} - {\min( {U_{3{pm}},V_{3{pm}},W_{3{pm}}} )}} \}}},$and the third sinusoidal drive function may be

${W_{2pm} = {\frac{2}{\sqrt{3}}M*\{ {W_{3pm} - {\min( {U_{3pm},V_{3pm},W_{3pm}} )}} \}}},{{{wherein}\mspace{14mu} U_{3pm}} = {\frac{1}{2}\sin\;\theta}},\;{V_{3pm} = {\frac{1}{2}si{n( {\theta - {\frac{2}{3}\pi}} )}}},{W_{3pm} = {\frac{1}{2}\;{\sin( {\theta - {\frac{4}{3}\pi}} )}}},$wherein M is a modulation ratio ranging from 0 to 1, and wherein θ is anangle of rotation of the three-phase motor.

The foregoing and other aspects, features, and advantages will beapparent to those artisans of ordinary skill in the art from theDESCRIPTION and DRAWINGS, and from the CLAIMS.

BRIEF DESCRIPTION OF THE DRAWINGS

Implementations will hereinafter be described in conjunction with theappended drawings, where like designations denote like elements, and:

FIG. 1 is a graph of voltage and current amplitude plotted as a functionof electric angle position of the rotor for an implementation of amethod of driving a three-phase motor;

FIG. 2 is a graph of torque plotted as a function of electric angleposition of the rotor for the method of FIG. 1 showing torque ripple;

FIG. 3 is a graph of voltage and current amplitude plotted as a functionof electric angle position of the rotor for an implementation of amethod of driving a three-phase motor;

FIG. 4 is a graph of torque plotted as a function of electric angleposition of the rotor for the method of FIG. 3;

FIG. 5 is a graph of torque plotted as a function of electric angleposition of the rotor for a method of driving a three-phase motor;

FIG. 6 is a graph of a Lissajous curve for the method of FIG. 3;

FIG. 7 is a graph of a Lissajous curve for a method similar to themethod of FIG. 3 except using a modulation ratio of 0.7;

FIG. 8 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 9 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 10 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 11 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 12 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 13 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 14 is a diagram representing control of a V phase in a method ofdriving a three-phase motor;

FIG. 15 is a diagram representing control of a V phase in a method ofdriving a three-phase motor;

FIG. 16 is a diagram representing control of a U phase in a method ofdriving a three-phase motor;

FIG. 17 is a diagram representing control of a V phase in a method ofdriving a three-phase motor;

FIG. 18 is a diagram representing windows for detecting a BEMF signalfor U, V and W phases in a method of driving a three-phase motor;

FIG. 19 is a diagram representing windows for detecting a BEMF signalfor U, V and W phases in a method of driving a three-phase motor;

FIG. 20 is a diagram representing windows for detecting a BEMF signalfor U, V and W phases in a method of driving a three-phase motor;

FIG. 21 is a diagram of a current vector in a method of driving athree-phase motor;

FIG. 22 is a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor;

FIG. 23 is a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor;

FIG. 24 is a graph of torque plotted as a function of electric angleposition of the rotor for the method of FIG. 22;

FIG. 25 is a graph of torque plotted as a function of electric angleposition of the rotor for the method of FIG. 23 showing an absence oftorque ripple;

FIG. 26 is a graph of a Lissajous curve for the method of FIG. 22;

FIG. 27 is a graph of a Lissajous curve for the method of FIG. 23;

FIG. 28 is a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor;

FIG. 29 is a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor;

FIG. 30 is a graph of torque plotted as a function of electric angleposition of the rotor for the method of FIG. 29 showing an absence oftorque ripple;

FIG. 31 is a graph of a Lissajous curve for the method of FIG. 29;

FIG. 32 is a circuit diagram representatively illustrating a circuit ofa controller used to control a three-phase motor;

FIG. 33 is a block diagram representatively illustrating a controllerused to control a three-phase motor;

FIG. 34 is a timing chart for a method of controlling a three-phasemotor;

FIG. 35 is a timing chart for a method of controlling a three-phasemotor;

FIG. 36 is a timing chart for a method of controlling a three-phasemotor; and

FIG. 37 is a block diagram representatively illustrating a three-phasemotor and elements used to control the three-phase motor and detect BEMFsignals.

DESCRIPTION

This disclosure, its aspects and implementations, are not limited to thespecific components, assembly procedures or method elements disclosedherein. Many additional components, assembly procedures and/or methodelements known in the art consistent with the intended drive methods ofthree phase motors will become apparent for use with particularimplementations from this disclosure. Accordingly, for example, althoughparticular implementations are disclosed, such implementations andimplementing components may comprise any shape, size, style, type,model, version, measurement, concentration, material, quantity, methodelement, step, and/or the like as is known in the art for such drivemethods of three phase motors, and implementing components and methods,consistent with the intended operation and methods.

During the operation of a three phase motor, for example at startup andat other times during operation, the motor controller needs to detectthe position and rotation speed of the rotor of the motor. Accuratelydoing so may allow for precise motor control by adjusting the timing ofan applied supply voltage to the motor windings. In some motors, Hallsensors may be used to detect the rotor position, but for sensor-lessmotors, the position may be detected using a back electromotive force(BEMF) signal, such as by comparing the BEMF signal with a voltage todetermine when the motor crosses the zero point.

During BEMF detection the phase used to detect the BEMF signal may betemporarily non-energized, causing a variation in output torque referredto as a “torque ripple.” Due to torque ripples the output torque of themotor may continuously vary between two or more values. Torque ripplesmay affect performance of a motor, reduce motor efficiency, increase thenoise produced by a motor, increase wear and tear of motor components,and decrease the life of motor components and the motor in general.

The methods disclosed herein include three-phase motor modulationmethods which improve drive torque ripple. Each phase of a three-phasemotor represents one of the windings of the motor stator. Inimplementations the methods may improve drive torque ripple in anN-window drive method. An N-window drive method is one which includeswindows where one phase is non-excited while its phase BEMF voltage isdetected. While different types of three-phase motors may benefit fromthe methods disclosed herein, one example of a motor that can be drivenusing the methods disclosed herein is a star-connected three-phasebrushless direct current (BLDC) motor. Another example is astar-connected three phase permanent magnet synchronous motor (PMSM orSPMSM). For perfect compensation of reduced torque during BEMF sensing amethod such as strict field orientation control (FOC) (vector control)could be applied. The methods disclosed herein do not use vector controland are useful for situations where it is desirable to improve(reduce/eliminate) torque ripple but where perfect compensation is notrequired and/or where vector control is prohibitively expensive orotherwise not an option. The methods disclosed herein include the use ofalgorithms used to drive three-phase motors, which driving may becontrolled by one or more integrated circuits. In one example theintegrated circuit is a field-programmable gate array (FPGA), though inother implementations other programmable and non-programmable (i.e.ASIC) circuit types could be used.

For N-window drive systems wherein one of the three phases isnon-excited while its phase BEMF voltage is detected, due to thenon-excited phase the system cannot apply an ideal drive-torque vectorto the motor and the motor operation includes torque ripples.

Referring now to FIG. 1, a graph representing control of a three-phasemotor includes voltage and current amplitudes plotted as a function ofelectric angle position of the rotor of the motor. The drive voltageamplitudes (U_(2pm), V_(2pm), W_(2pm), wherein U, V and W are the phasesand 2 pm represents two phase modulation with a non-exciting phase)represent motor terminal voltage and are plotted using a line, a dashedline, and a dashed and dotted line, respectively. The phase drivecurrent amplitudes (IU, IV, and IW) represent phase current (motorstator current) and are plotted using squares, triangles, and circles,respectively. For simplicity, the stator inductances and BEMF voltagesare omitted for ease of viewing the other details of the graph. Theelectric angle position of the rotor is given in radians. It may be seenfrom the current amplitudes that the current of each phase is generallysinusoidal, but that for each phase there are windows where the currentis intentionally zero for a period of time. This is the N-window and mayotherwise be referred to as a HiZ (high impedance) state for that phase.For example, when the U phase is in a zero phase current window(N-window or HiZ window) the BEMF zero-cross point may be determined fordetermining the rotor position of the motor. During this HiZ window thetorque of the motor decreases, resulting in the previously discussedtorque ripples. It is pointed out that, while the currents are generallysinusoidal, the applied voltage amplitudes are also generally sinusoidalexcept at the HiZ windows. In this example a modulation ratio of 0.6 isused.

FIG. 2 representatively illustrates the torque of the three phase motorof FIG. 1 plotted against the electric angle of the rotor of the motor(this time represented in degrees). The torque is represented by q-axiscurrent converted by the Clarke-Park transformation, the q-axis currentrepresenting generated torque. The torque ripples are visually seen inFIG. 2, with the torque dipping low in several places, each of thesedips corresponding with a HiZ window of one of the phases.

FIG. 3 shows another example of a graph of voltage and current amplitudeplotted as a function of electric angle position for an N-window drivemethod. Apart from the plotted values, the characteristics/details ofthis graph are similar to those described above for FIG. 1. In thisexample the phase currents are again seen to be relatively sinusoidalbut to have HiZ periods where the current is intentionally zero for aperiod of time. The graph of FIG. 3 includes windows 2 which indicateperiods wherein a non-exciting phase is used to detect a phase BEMFvoltage. The drive method of FIG. 3 uses a modulation ratio of 1.0.

FIG. 4 representatively illustrates torque plotted as a function ofelectric angle position of the rotor for the drive method of FIG. 3.Apart from the plotted values, the characteristics/details of this graphare similar to those described above for FIG. 2. Torque ripples areagain seen. Windows 4 shown on the graph align with the torque ripplesand also align with the HiZ windows 2 of FIG. 3, and it is seen that thetorque ripples correspond with the HiZ windows. FIG. 5 represents atorque plot for a drive method similar to that of FIG. 3 except wherethe drive method uses a modulation ratio of 0.7. The torque ripples arestill seen in the windows 6 which correspond with HiZ windows of thedrive method where a phase BEMF voltage is detected.

FIG. 6 shows a Lissajous curve of drive current converted by the Clarketransformation for the drive method of FIG. 3 with a 1.0 modulationratio. The I-Alpha axis is the Alpha-axis current and the I-Beta axis isthe Beta-axis current. The Lissajous curve shows where the torque iswhen the current is applied and the motor is applied. Where there are nocircles on the curve, this indicates the torque jumping from one valueto another—these locations correspond with the torque ripples of FIGS. 4and 5. FIG. 7 shows a Lissajous curve of drive current converted by theClarke transformation for a drive method similar to the method of FIG. 3except using a 0.7 modulation ratio. Other than the plotted values, thecharacteristics/details of the graph of FIG. 7 are similar to those ofFIG. 6.

When an original drive modulation ratio for a drive method is less than100%, two phases (the phases other than the current HiZ, non-excitedphase) can be modulated by a ratio greater than the original modulationratio to decrease the reduction in torque caused by the HiZ window. Themotor torque is generated by q-axis current and the q-axis current is avector (stator current vectors of three phases are projected to theq-axis).

As mentioned above the N-window drive methods include a non-excitingtime periods. In this disclosure the N-period or non-excited period forany given phase is referred to as a window period, whereas an excitingperiod for any given phase is referred to as an energization period. Forany given phase an energization period starts when a window period ends,and when a window period starts an energization period ends. When anygiven phase is in an energization period there are two potentialsituations. Either all phases are in an energization period (termedherein as an ALLENG period) or one phase other than the given phase isin a window period (termed herein as a WNDENG period).

As a simple example, returning to FIG. 3 it may be seen that at anelectric angle position of π/3 (˜1.0471976) the V phase has a negativecurrent, the U phase has a positive current, and the W phase is at zerocurrent. From the perspective of the V phase or the U phase, this wouldbe a WNDENG period. At an electric angle position of π/6 (˜0.523599) theV phase has a negative phase current and the U and W phases both havepositive phase current. This would accordingly be an ALLENG period.Whether a phase is “energized/excited” or in an “energized/excitedstate,” as those terms are used herein, is accordingly determined by thephase's current being either zero (non-energized/excited) or having anon-zero value (energized/excited), and not whether the phase drivevoltage is zero or non-zero. For example, in FIG. 3 it may be seen thatat the electric angle position of π/6 (˜0.523599) the V phase has zerodrive voltage while the U and W phases both have a positive drivevoltage. The zero drive voltage for the V phase does not mean that the Vphase is not energized/excited because, as defined herein, the phase isexcited/energized if the phase current is non-zero. Similarly, at theelectric angle position of π/3 (˜1.0471976) the W phase isnon-energized/non-excited, even though it has a positive/non-zerovoltage, because it has zero phase current.

Furthermore, still making reference to FIG. 3 and also making referenceto FIG. 32 which describes a circuit diagram that may be used in acontroller controlling the three-phase motor, and ignoring Rsresistance, at the electric angle position of π/3 (˜1.0471976) theinverter's Q1H and Q1L are switching using pulse width modulation (PWM),Q2H is OFF and Q2L is ON, and Q3H and Q3L are OFF. UOUT thereforeoutputs non-zero volts, VOUT outputs zero volts, and WOUT outputs theHiZ state. As PWM is performed with synchronous rectification and themotor's stator is an inductance load, there are generating currents andregenerative currents (also a zero volt/zero drive node may operate as asink node for another source node). During this angle position althoughVOUT outputs zero volts, IV (V phase current) is flowing via the U phase(meaning UOUT is a source node and VOUT is a sink node). Accordingly,even if VOUT outputs zero volts during this time period, the motor's Vphase is energized via the U phase. At this same time period, however,IW (W-phase current) is not flowing, even though WOUT has a positivevoltage, because its positive voltage is not drive voltage based on theWOUT output, so the W phase is not energized/excited. Node voltageduring a non-energized period indicates a generated voltage (fromimpedance of the other two phases) and has a value of the sum of theother two phase voltages divided in half. BEMF voltage is overlappedwith this period but, as indicated, is not included in the drawings forsimplicity.

Referring now to FIG. 8, a diagram is illustrated that representscontrol of a U phase in a method of driving a three-phase motor. Thisgraph diagrams voltage drive amplitude for the phase plotted against theelectric angle of the rotor (in radians). At the top of this graph arecalled out “Window Period of Self-Phase” portions which are windowperiods for the U phase or, in other words, periods where the U phasemay be placed in a HiZ state (with zero phase current) to perform a BEMFdetection. Also called out are “Energization Period” portions whichindicate periods where the U phase has a non-zero phase current (even ifthe drive voltage is zero) so that the U phase is “energized.” It isalso illustrated that the energization periods alternate between ALLENGperiods (where all phases are energized) and WNDENG periods (where oneother phase is not energized). In this example there are six windows—twofor the U phase itself (the first and last window periods being halvesof a single window), two for the W phase, and two for the V phase. Eachsection accordingly represents 30 degrees of rotation of the rotor.Similar graphs could be prepared for control of the V phase and the Wphase. This diagram is an example of control of a phase in 6-windowmode.

The graph of FIG. 8 represents control of the U phase without modifyingvoltage during the WNDENG periods, and accordingly the torque ripplesdiscussed above would be present. FIG. 9, on the other hand, shows asimilar graph for the U phase, in 6-window mode with 30-degree windows,but wherein when a positive voltage is being applied to the U phase andwhen a WNDENG window is reached, the applied voltage to the U phaseswitches temporarily from a sinusoidal waveform to a different waveform.The different waveform results in an increased voltage for the U phase.In this example the modulation ratio is 1.0. The HiZ periods/windows forthe U phase are also shown in this graph. The ALLENG periods for the Uphase are controlled based on a first 2-phase modulation waveform andthe WNDENG periods for the U phase are controlled by a second 2-phasemodulation waveform. In implementations the second 2-phase modulationwaveform could be a processed or modified version of the first waveform,or it could be an entirely different waveform not based on the firstwaveform. In either case, the second waveform (and, in general, thedifferent waveforms during the WNDENG periods) are termed herein as lowtorque ripple (LTR) modulation waveforms, as they reduce torque ripple.Although the graph of FIG. 9 focuses on the U phase, graphs depictingthe control/drive voltages of the V and W phases would be similar (butoffset by 120 degrees and 240 degrees from the U phase, respectively).

FIG. 10 is a diagram representing control of a U phase in a method ofdriving a three-phase motor and is similar to FIG. 9 except that amodulation ratio of 0.7 is used. Again, when a positive voltage is beingapplied to the U phase and a WNDENG window is reached, the appliedvoltage to the U phase switches temporarily from a sinusoidal waveformto a different waveform (LTR waveform). The LTR waveform is seen to bedifferent from what it was for the 1.0 modulation ratio version of FIG.9 but, still, generally results in an increase in voltage for at leastsome of the WNDENG periods compared with what would be applied using theoriginal sinusoidal wave function. It is seen that for the WNDENGperiods where the U phase has zero applied voltage the applied voltageremains at zero. Nevertheless, at these WNDENG windows the appliedvoltage to other phases may be increased to reduce torque ripple.Although the graph of FIG. 10 focuses on the U phase, graphs depictingthe control/drive voltages of the V and W phases would be similar (butoffset by 120 degrees and 240 degrees from the U phase, respectively).

The LTR waveforms used during the WNDENG windows decrease the dip intorque at the HiZ windows. Accordingly, even though one of the threephases of the motor stator is in a non-excited state, the reduction intorque is not as great as it would be. The substituted LTR waveform isaccordingly defined so that torque ripple is reduced. Inimplementations, when one phase is non-excited, the other two phases areexcited and are driven by substituting the LTR drive value(s) instead ofthe normal sinusoidal drive values. In other implementations, when onephase is non-excited, the other two phases are excited but only one ofthem is driven by substituting the LTR drive value(s) instead of thenormal sinusoidal drive values. In the implementations described andshown herein the substituted drive values are tailored to astar-connection stator. In other implementations, however, theprinciples and methods disclosed herein may be adapted to be used withother types of motors. The graphs of FIGS. 9 and 10, as indicated, have6 WNDENG windows. This is the maximum amount of windows per an electricangle period of the rotor for substituting LTR drive values in place ofthe normal sinusoidal drive value(s). The segment width is definedwithin +/−30 degrees centered at zero-cross points of phase BEMF.

FIG. 11 shows a diagram representing control of a U phase in a method ofdriving a three-phase motor, in 3-window mode with 30-degree windows.When a positive voltage is being applied to the U phase and a WNDENGwindow is reached, the applied voltage to the U phase switchestemporarily from a sinusoidal waveform to an LTR waveform. The LTRwaveform results in an increased drive voltage for at least part of theWNDENG period relative to the normal sinusoidal drive waveform. When theWNDENG window is ended, the applied voltage to the U phase switches backto the normal sinusoidal waveform. In this example the modulation ratiois 1.0. The HiZ periods/windows for the U phase are also shown in thisgraph. Although the graph of FIG. 11 focuses on the U phase, graphsdepicting the control/drive voltages of the V and W phases would besimilar (but offset by 120 degrees and 240 degrees from the U phase,respectively).

FIG. 12 is a diagram representing control of a U phase in a method ofdriving a three-phase motor and is similar to FIG. 11 except that amodulation ratio of 0.7 is used. Again, when a positive voltage is beingapplied to the U phase and a WNDENG window is reached, the appliedvoltage to the U phase switches temporarily from a sinusoidal waveformto an LTR waveform. When the WNDENG window is ended, the applied voltageto the U phase switches back to the normal sinusoidal waveform. The LTRwaveform is seen to be different from what it was for the 1.0 modulationratio version of FIG. 11 but, still, generally results in an increase involtage for at least some of the WNDENG periods compared with what wouldbe applied using the original sinusoidal wave function. It is seen thatfor the WNDENG periods where the U phase has zero applied voltage theapplied voltage remains at zero. Nevertheless, at these WNDENG windowsthe applied voltage to other phases may be increased to reduce torqueripple. Although the graph of FIG. 12 focuses on the U phase, graphsdepicting the control/drive voltages of the V and W phases would besimilar (but offset by 120 degrees and 240 degrees from the U phase,respectively).

FIG. 13 shows a diagram representing control of a U phase in a method ofdriving a three-phase motor in 2-window mode with 30-degree windows. Inthis case there are no WNDENG windows because in the 2-window mode the Vphase and W phase do not have HiZ windows/periods. Accordingly, the Uphase is controlled by the normal sinusoidal waveform without any LTRwaveform.

FIG. 14, however, shows a diagram representing control of a V phase in amethod of driving a three phase motor in 2-window mode with 30 degreewindows. When a positive voltage is being applied to the V phase and aWNDENG window is reached (for a U phase HiZ window), the applied voltageto the V phase switches temporarily from a sinusoidal waveform to an LTRwaveform. The LTR waveform results in an increased drive voltage for atleast part of the WNDENG period relative to the normal sinusoidal drivewaveform. When the WNDENG window is ended, the applied voltage to the Vphase switches back to the normal sinusoidal waveform. In this examplethe modulation ratio is 1.0. This graph also shows that the V phase hasno HiZ periods/windows. Although the graph of FIG. 14 focuses on the Vphase, a graph depicting the control/drive voltage of the W phase wouldbe similar (but offset by 120 degrees from the V phase).

FIG. 15 is a diagram representing control of a V phase in a method ofdriving a three-phase motor and is similar to FIG. 14 except that amodulation ratio of 0.7 is used. Again, when a positive voltage is beingapplied to the V phase and a WNDENG window is reached (for a U phase HiZwindow), the applied voltage to the V phase switches temporarily from asinusoidal waveform to an LTR waveform. When the WNDENG window is ended,the applied voltage to the V phase switches back to the normalsinusoidal waveform. The LTR waveform is seen to be different from whatit was for the 1.0 modulation ratio version of FIG. 14 but, still,generally results in an increase in voltage for at least some of theWNDENG period compared with what would be applied using the originalsinusoidal wave function. It is seen that for the WNDENG periods wherethe V phase has zero applied voltage the applied voltage remains atzero. Nevertheless, at these WNDENG windows the applied voltage to the Wphase may be increased to reduce torque ripple. Although the graph ofFIG. 15 focuses on the V phase, a graph depicting the control/drivevoltages of the W phase would be similar (but offset by 120 degrees fromthe V phase).

FIG. 16 shows a diagram representing control of a U phase in a method ofdriving a three-phase motor in 1-window mode with 30-degree windows. Inthis case there are no WNDENG windows because in the 1-window mode the Vphase and W phase do not have HiZ windows/periods. Accordingly, the Uphase is controlled by the normal sinusoidal waveform without any LTRwaveform.

FIG. 17 shows a diagram representing control of a V phase in a method ofdriving a three-phase motor in 1-window mode with 30-degree windows. Inthis case there is a WNDENG window but it does not correspond with apositive voltage being applied to the V phase, so the V phase is notmodified from its normal sinusoidal waveform. The modulation ratio ofFIG. 17 is 1.0. A figure is not provided representing control of the Wphase in a method of driving a three-phase motor in 1-window mode with30-degree windows, but the W phase would be offset from the V phase by120 degrees to that the positive applied voltage to the W phase wouldoverlap with the WNDENG window for the U phase. Accordingly, during theWNDENG window the W phase would be driven by the LTR waveform whichwould, for at least part of the WNDENG period, result in an increasedapplied voltage relative to the normal sinusoidal waveform. After theWNDENG period passes the W phase would return to the normal sinusoidalwaveform. Qualitatively the difference in the applied voltage to the Wphase during the WNDENG period between the 1.0 modulation ratio and a0.7 modulation ratio would be similar to the difference between theapplied voltage to the V phase during the WNDENG period between the 1.0modulation ratio and 0.7 modulation ratio shown in FIGS. 14 and 15.

There are limits to the window periods for each phase. The limits of thewindow period (in degrees) is seen in TABLE 1 below.

TABLE 1 Phase Limit of Window Period (degrees) U 330 ≤θ <360, 0 ≤θ <30,150 ≤θ <210 V 90 ≤θ <150, 270 ≤θ <330 W 30 ≤θ <90, 210 ≤θ <270

FIG. 18 shows the maximum window period for the three phases when amodulation ratio of 1.0 is used and when no LTR waveform is used. Thedifferent cross-hatched portions reflect the windows. For example, the Wphase is seen to have a first window between 30 and 90 degrees. Inradians this is about 0.52 radians to 1.57 radians. Accordingly, on thegraph of FIG. 18 there is a first W portion with the letter W close tothe W curve but, also, within a first cross-hatched portion from theleft of the graph that has lines sloping downwards towards the right.This W portion is depicted between about 0.52 radians and about 1.57radians, corresponding with the 30 and 90 degrees. The next W portion(with similar cross-hatching) is depicted between 210 and 270 degrees(but, in FIG. 18, in radians). FIG. 19 similarly shows the maximumwindow period for the three phases when a modulation ratio of 1.0 isused and when LTR waveforms are used. FIG. 20 shows the maximum windowperiod for the three phases when the modulation ratio is 0.7 and LTRwaveforms are used. If a BEMF zero-cross has not been able to bedetected by the end of a limit as indicated in TABLE 1, the HiZ statusis ended according to the limit of the window period. In such a case forcontinuing operation an interpolation would be performed by the “RotorPosition/Speed Generator” block of the system (illustrated in FIG. 37).

Representative examples of drive functions for the three phases inimplementations wherein LTR modulation is used are given below.

$U_{2{pm}} = \{ {{\begin{matrix}{{\frac{2}{\sqrt{3}}M\{ {U_{3{pm}} - {\min( {U_{3pm},V_{3pm},W_{3pm}} )}} \}},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{ALLENG}\mspace{14mu}{perod}} \\{U_{ltrm},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{WNDENG}\mspace{14mu}{period}} \\{{HiZ},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu} U\mspace{14mu}{window}\mspace{14mu}{period}}\end{matrix}V_{2{pm}}} = \{ {{\begin{matrix}{{\frac{2}{\sqrt{3}}M\{ {V_{3{pm}} - {\min( {U_{3pm},V_{3pm},W_{3pm}} )}} \}},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{ALLENG}\mspace{14mu}{period}} \\{V_{ltrm},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{WNDENG}\mspace{14mu}{period}} \\{{HiZ},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu} V\mspace{14mu}{window}\mspace{14mu}{period}}\end{matrix}W_{2{pm}}} = \{ \begin{matrix}{{\frac{2}{\sqrt{3}}M\{ {W_{3{pm}} - {\min( {U_{3pm},V_{3pm},W_{3pm}} )}} \}},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{ALLENG}\mspace{14mu}{period}} \\{W_{ltrm},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu}{WNDENG}\mspace{14mu}{period}} \\{{HiZ},} & {{When}\mspace{14mu}\theta\mspace{14mu}{is}\mspace{14mu} W\mspace{14mu}{window}\mspace{14mu}{period}}\end{matrix} } } $

In the above equations some of the values are calculated as follows:U _(3pm)=₂ ¹ sin θV _(3pm)=₂ ¹ sin(θ−₃ ²π)W _(3pm)=₂ ¹ sin(θ−₃ ⁴π)

The variables in the above equations are defined as follows:

-   U_(2pm): U-phase 2-phase modulation waveform (fundamental wave of    N-window method)-   V_(2pm): V-phase 2-phase modulation waveform (fundamental wave of    N-window method)-   W_(2pm): W-phase 2-phase modulation waveform (fundamental wave of    N-window method)-   U_(3pm): U-phase 3-phase modulation waveform-   V_(3pm): V-phase 3-phase modulation waveform-   W_(3pm): W-phase 3-phase modulation waveform-   U_(ltrm): U-phase modulation waveform during a window [low torque    ripple (LTR) modulation]-   V_(ltrm): V-phase modulation waveform during a window [low torque    ripple (LTR) modulation]-   W_(ltrm): W-phase modulation waveform during a window [low torque    ripple (LTR) modulation]-   θ: Rotor position in electric-angle-   M: Modulation ratio (0 to 1)

In this representative example, when one of the three phases is in thewindow period, the normal sinusoidal waveform would result in a decreaseof torque. LTR modulation is accordingly applied during the window toreduce torque ripple. In practice LTR modulation should be operatedconsidering a transfer function of a motor stator, though this isignored herein for simplification and to highlight other aspects of LTRmodulation. TABLE 2 below gives modulation ratio assignments forU_(ltrm), V_(ltrm) and W_(ltrm) for different values of θ.

TABLE 2 θ (degrees) U_(ltrm) V_(ltrm) W_(ltrm)  0 ≤θ <30 HiZ 0 M_(ltr) 30 ≤θ <90 M_(ltr) 0 HiZ  90 ≤θ <150 M_(ltr) HiZ 0 150 ≤θ <210 HiZM_(ltr) 0 210 ≤θ <270 0 M_(ltr) HiZ 270 ≤θ <330 0 HiZ M_(ltr) 330 ≤θ<360 HiZ 0 M_(ltr)

The value of M_(ltr) in this representative example is given by thefollowing equation.

$M_{ltr} = \{ \begin{matrix}{{\frac{M}{\cos( {\theta - \theta_{wc}} )}}\ ,} & {{{When}\ {\frac{M}{\cos( {\theta - \theta_{wc}} )}}}\  < 1} \\{1,} & {{{When}\ {\frac{M}{\cos( {\theta - \theta_{wc}} )}}}\  \geq 1}\end{matrix} $

In the above equation M is a modulation ratio ranging from 0 to 1, andθ_(wc), which is a center phase position of the maximum window period,is given by TABLE 3 below.

TABLE 3 θ (degrees) θ_(wc) (degrees)  0 ≤θ <30 0  30 ≤θ <90 60  90 ≤θ<150 120 150 ≤θ <210 180 210 ≤θ <270 240 270 ≤θ <330 300 330 ≤θ <360 0

FIG. 21 shows a vector diagram of a current vector in LTR modulation. Inthis example, “d” represents the rotor's d-axis and “q” represents therotor's q-axis. For this graph it is assumed that the motor's stator isconfigured by a star connection, that each phase resistance is 1 ohm,and that the rotor position is 0≤θ<30 or 330≤θ<360.

FIG. 22 shows a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor that includes LTR modulation.This graph omits stator inductances and BEMF voltage for simplification.The drive phase voltages and drive phase currents are shown and, otherthan the plotted values, the characteristics/details of this graph aresimilar to those of FIG. 1. A modulation ratio of 1.0 is used in thisdrive method.

When a positive voltage is being applied to a phase and a WNDENG windowis reached, the applied voltage to that phase switches temporarily froma sinusoidal waveform to an LTR waveform. The LTR waveform results in anincreased drive voltage for at least part of the WNDENG period relativeto the normal sinusoidal drive waveform. When the WNDENG window isended, the applied voltage to the phase switches back to the normalsinusoidal waveform. The HiZ periods/windows for the phases are alsoseen in this graph.

FIG. 23 shows a graph of voltage and current amplitude plotted as afunction of electric angle position of the rotor for an implementationof a method of driving a three-phase motor that includes LTR modulation.This graph is similar to FIG. 22 except that a modulation ratio of 0.7is used. This graph omits stator inductances and BEMF voltage forsimplification. The drive phase voltages and drive phase currents areshown and, other than the plotted values, the characteristics/details ofthis graph are similar to those of FIG. 1. When a positive voltage isbeing applied to a phase and a WNDENG window is reached, the appliedvoltage to that phase switches temporarily from a sinusoidal waveform toan LTR waveform. The LTR waveform for the 0.7 modulation ratio is seento be different than that for the 1.0 modulation ratio but, still,results in an increased drive voltage for at least part of the WNDENGperiod relative to the normal sinusoidal drive waveform. When the WNDENGwindow is ended, the applied voltage to the phase switches back to thenormal sinusoidal waveform. The HiZ periods/windows for the phases arealso seen in this graph.

In the examples of FIGS. 22-23 the electric angle positions and widthsof the window periods are 0 degrees+/−15 degrees, 60 degrees+/−15degrees, 120 degrees+/−15 degrees, 180 degrees+/−15 degrees, 240degrees+/−15 degrees, and 300 degrees+/−15 degrees.

FIG. 24 representatively illustrates the torque of the three phase motorof FIG. 22 plotted against the electric angle of the rotor of the motor(this time represented in degrees). The torque is represented by q-axiscurrent converted by the Clarke-Park transformation, the q-axis currentrepresenting generated torque. The torque ripples are visually seen inFIG. 24, with the torque dipping low in several places, each of thesedips corresponding with a HiZ window of one of the phases. The torqueripples are improved relative to the torque ripples of FIG. 4, but theyare still present.

FIG. 25 representatively illustrates the torque of the three phase motorof FIG. 23 plotted against the electric angle of the rotor of the motor(this time represented in degrees). The torque is represented by q-axiscurrent converted by the Clarke-Park transformation, the q-axis currentrepresenting generated torque. In this graph the torque ripples are nolonger seen. Accordingly, this graph is an example of a graph plotting agenerated torque of the three-phase motor on a y-axis and a rotor angleposition of a rotor of the three-phase motor on an x-axis that displaysno variation in the generated torque over at least one powered360-degree rotation of the rotor (single torque value over a powered 360degree rotation). This shows that for the LTR modulation equations givenabove, when the modulation ratio M is 1, the torque ripple remains, butwhen the modulation ratio M is lowered to 0.7, the ripple is adequatelydecreased so that it does not appear on the graph of FIG. 25. It ispossible that, in implementations, modulation ratios above 0.7 couldalso result in a decrease in torque ripple significant enough to presenta graph similar to FIG. 25. It is also expected that modulation ratiosbelow 0.7 would result in graphs similar to FIG. 25 showing no torqueripple.

The decrease in torque ripple may result in increased life of the motor,reduced wear and tear to the motor and its components, more silentoperation, more efficient operation, and so forth. As a non-limitingexample, in a fan motor application, a smaller modulation ratio wouldusually mean a lower speed operation for the motor and in this case italso results in lower torque ripple, which reduces the vibration andnoise of the fan.

FIG. 26 shows a Lissajous curve of drive current converted by the Clarketransformation for the drive method of FIG. 22 with a 1.0 modulationratio. The I-Alpha axis is the Alpha-axis current and the I-Beta axis isthe Beta-axis current. The Lissajous curve shows where the torque iswhen the current is applied and the motor is applied. Where there are nocircles on the curve this indicates the torque jumping from one value toanother—these locations correspond with the torque ripples of FIG. 24.FIG. 27 shows a Lissajous curve of drive current converted by Clarketransformation for the drive method of FIG. 23 using a 0.7 modulationratio. Other than the plotted values, the characteristics/details of thegraph of FIG. 27 are similar to those of FIG. 26. Nevertheless, althoughthere are locations where circles are not present, the torque ripplesare not evident in the graph of FIG. 25. These Lissajous curves alsoshow, when compared with the graphs of FIGS. 6 and 7, that the drivecurrent values themselves are changed between the LTR-modulated andnon-LTR-modulated versions.

Lead angle control will now be discussed. Lead angle control adds offsetinto a phase position to generate a modified drive voltage waveform. Asan example, when LTR modulation as described above is used and when amodulation ratio of 0.7 is used, then when the lead angle is 0 thegenerated drive voltage waveform would be given as indicated in FIG. 23.On the other hand, if the lead angle amount is changed to 15 degrees,the drive waveform is generated as shown in FIG. 28. Both FIGS. 23 and28 are drawn assuming that 0 radians is the point of U phase risingabove the BEMF zero-cross point.

Accordingly, when the lead angle is considered, the U_(2 pm), V_(2pm)and W_(2pm) equations above should be implemented considering the leadangle amount. But TABLES 2 and 3 and the M_(ltr) equation above shouldbe implemented by θ information not considering lead angle. This meansthat the θ information used to determine the basic 2-phase modulationwaveform should include a lead angle amount, but the window period andLTR modulation should be operated by θ information not including leadangle amount.

Referring now to FIG. 29, another example of a graph of voltage andcurrent amplitude plotted as a function of electric angle position ofthe rotor for an implementation of a method of driving a three-phasemotor (including LTR modulation) is shown. This method departs from themethods and equations disclosed above in that, as soon as BEMF isdetected, the LTR modulated phase returns to the normal sinusoidal phase(ALLENG) instead of being driven by the LTR modulation for the entireWNDENG window. In implementations this increases efficiency and reducestorque ripple even further for reduced noise, improved life of the motorand reduced wear and tear, etc. The example in FIG. 29 uses a modulationratio of 0.6 and the HiZ windows are shown. Apart from the plottedvalues, the characteristics/details of FIG. 29 are similar to those ofFIG. 1. In another representative example a predetermined time could beselected, and the LTR modulation could be used to drive the phasevoltage only until the predetermined time, the predetermined time beingselected to be enough time to detect BEMF but still only a fraction lessthan the full WNDENG window.

In the implementation of FIG. 29 the electric angle positions and widthsof the window periods are 0 degrees+0/−15 degrees, 60 degrees+0/−30degrees, 120 degrees+0/−15 degrees, 180 degrees+0/−15 degrees, 240degrees+0/−15 degrees, and 300 degrees+0/−15 degrees.

FIG. 30 representatively illustrates the torque of the three phase motorof FIG. 29 plotted against the electric angle of the rotor of the motor(represented in degrees). The torque is represented by q-axis currentconverted by the Clarke-Park transformation, the q-axis currentrepresenting generated torque. In this graph the torque ripples areagain not observed. Accordingly, this graph is another example of agraph plotting a generated torque of the three-phase motor on a y-axisand a rotor angle position of a rotor of the three-phase motor on anx-axis that displays no variation in the generated torque over at leastone powered 360-degree rotation of the rotor.

FIG. 31 shows a Lissajous curve of drive current converted by the Clarketransformation for the drive method of FIG. 29. Other than the plottedvalues, the characteristics/details of the graph of FIG. 31 are similarto those of FIG. 27. Nevertheless, although there are locations wherecircles are not present, the torque ripples are not evident in the graphof FIG. 30. This Lissajous curve also shows, when compared with thegraph of FIG. 7, that the drive current values are changed between theLTR modulated and non-LTR-modulated versions.

Referring now to FIG. 32, an example of a three-phase inverter circuitthat may be used in or with a control module to control a three-phasemotor, according to the methods disclosed herein, is shown. Thethree-phase inverter circuit uses three half bridges to drive the motor.As an example of driving just the U phase, when drive voltage is appliedto the U phase the UH is pulsed on and off using PWM. When UH is on ULis off and vice-versa. When the drive voltage for the U phase is zerothen UL stays on and UH stays off.

Referring now to FIG. 33, a block diagram representatively illustrates acontroller (which in particular implementations may be implemented in anintegrated circuit) for controlling a three phase motor using themethods disclosed herein. Various elements are shown including anencoder module/component, an LTR (low torque ripple) Modulationmodule/component, a 2-Phase Modulation module/component, and so forth. Apulse width modulation (PWM) module is not shown but electricconnections to be coupled with a PWM module are representativelyillustrated.

The inputs of the controller of FIG. 33 include the following: CLK(operation clock); RSTX (reset—0 is reset and 1 is active); RPOS[9:0](rotor's position information—θ) (rotor position information is based ondetected BEMF zero-cross signal, 0.352deg/LSB); LA[7:0] (lead angleamount/value—θ_(la)) (0.352deg/LSB); M[9:0] (output modulation ratio—M,full scale is 100%, 0 is 0%); HIZU (non-exciting window period statusflag of U-phase, 1: window period, 0: normal); HIZV (non-exciting windowperiod status flag of V-phase, 1: window period, 0: normal); HIZW(non-exciting window period status flag of W-phase, 1: window period, 0:normal); CALCUPD (update event flag for calculating next value—when thisflag has risen, the next value is updated by input values of thatmoment).

The outputs of the controller of FIG. 33 include the following:DRVDUTYU[9:0] (drive PWM duty ratio, U-phase, full scale is 100%, 0 is0%); DRVDUTYV[9:0] (drive PWM duty ratio, V-phase, full scale is 100%, 0is 0%); DRVDUTYW[9:0] (drive PWM duty ratio, W-phase, full scale is100%, 0 is 0%).

It is also pointed out that RPOSLA=RPOS+LA. WNDENGU, WNDENGV and WNDENGWcorrespond to WNDENG windows for U, V, and W phases, respectively. HIZU,HIZV and HIZW are provided from an external module. The completeN-window drive waveform including a non-exciting phase is finished usinga PWM module, not illustrated in FIG. 33 but coupled with thecontroller.

Referring now to FIGS. 34-36, a number of timing charts are given.Calculation for these timing function must be completed within onedrive-PWM period. TCALC shown in FIGS. 34-36 represents calculationtime, and should be determined according to actual design. The period ofCALCUPD should be matched with the drive-PWM carrier period, but theassertion timing should be designed optimally within the PWM carrierperiod to minimize system delay with respect to RPOS and LA information.This means that TCALC is important to optimize the design to ensure thatthe timing is set up to correspond with the drive-PWM carrier period.

FIG. 34 is an example of a timing chart in a case where HIZU=1 and0≤θ<30 or 330≤θ<360. In the case of 150≤θ<210, as long as DRVDUTYVoutput is alternated with LTR modulation and DRVDUTYW output isalternated with 2-phase modulation, the timing is similar to FIG. 34.

FIG. 35 is an example of a timing chart in a case where HIZV=1 and90≤θ<150. In the case of 270≤θ<330, as long as DRVDUTYW output isalternated with LTR modulation and DRVDUTYU output is alternated with2-phase modulation, the timing is similar to FIG. 35.

FIG. 36 is an example of a timing chart in a case where HIZW=1 and210≤θ<270. In the case of 30≤θ<90, as long as DRVDUTYU output isalternated with LTR modulation and DRVDUTYV output is alternated with2-phase modulation, the timing is similar to FIG. 36.

FIG. 37 is a block diagram representatively illustrating a three-phasemotor and elements used to control the three-phase motor and detect BEMFsignals. In this representative example, the three-phase inverter andBEMF detector are separate individual modules, while everything to theleft of these is implemented on a single semiconductor device. In thisexample the LTR modulation methods disclosed herein are implementedusing the “2-Phase Mod w/LTR mod” block. The configuration of FIG. 37applies only to star-configuration three-phase motors.

In implementations modulation ratios disclosed herein may be determinedby system capacity, wherein a modulation ratio of 1.0 is full systemcapacity (of applied voltage) and lower modulation ratios are acorresponding percentage of full system capacity.

It is pointed out that TABLE 2 includes values only for a 6-window mode.However, the U_(2pm), V_(2pm), W_(2pm) equations are given priority overTABLE 2. When 1-window, 2-window or 3-window modes are used, the ALLENGperiod increases over a 6-window ALLENG period, and WNDENG period andwindow periods decrease. Because of this, LTR modulation can be definedbased on the TABLE 2 values even though they technically only represent6-window mode.

It is further pointed out that the start timing of a non-energizedportion can be decided on according to the respective application, andthe end time of the non-energized portion can be decided adaptively (orusing a predetermined time). When the start timing is far from BEMFzero-cross the robustness for detection will increase but the torqueripple will not be reduced as much.

In places where the description above refers to particularimplementations of drive methods for three phase motors and implementingcomponents, sub-components, methods and sub-methods, it should bereadily apparent that a number of modifications may be made withoutdeparting from the spirit thereof and that these implementations,implementing components, sub-components, methods and sub-methods may beapplied to other drive methods for three phase motors.

What is claimed is:
 1. A method of driving a star-connected three-phasemotor, comprising: while a first phase of the star-connected three-phasemotor is in an energized state, driving a second phase of thethree-phase motor using a first sinusoidal drive function; switching thefirst phase to a non-energized state; while the first phase is in thenon-energized state, detecting a first back electromotive force (BEMF)voltage of the first phase; and for at least a portion of a time whenthe first phase is in the non-energized state, driving the second phaseusing a second drive function that varies from the first sinusoidaldrive function to generate torque with no variation in the torque over apowered 360 degree rotation of the three-phase motor.
 2. The method ofclaim 1, wherein the three-phase motor comprises one of a sensorlessbrushless direct current (BLDC) motor and a permanent magnet synchronousmotor (PMSM).
 3. The method of claim 1, wherein driving the second phaseusing the second drive function results in an increased voltage appliedto the second phase relative to driving the second phase using the firstsinusoidal drive function.
 4. The method of claim 1, further comprising,while the first phase is in a second non-energized state, driving athird phase of the three-phase motor using a third drive function thatvaries from a second sinusoidal drive function.
 5. The method of claim4, wherein driving the third phase using the third drive functionresults in an increased voltage applied to the third phase relative todriving the third phase using the second sinusoidal drive function. 6.The method of claim 1, further comprising, after driving the secondphase using the second drive function until the first BEMF voltage isdetected, driving the second phase using the first sinusoidal drivefunction.
 7. The method of claim 1, further comprising, after drivingthe second phase using the second drive function for a predeterminedamount of time, driving the second phase using the first sinusoidaldrive function.